Method of Estimating the Symbols of a Digital Signal and Receiver for Implementing Said Method

ABSTRACT

The invention relates to a method of estimating symbols carried by a digital signal that is received by a receiver over a communication channel ( 5 ), said symbols being multiplexed or orthogonal frequency sub-carriers. The inventive method comprises the following steps in relation to each symbol carried by the digital signal, consisting in: performing at least two transforms towards the frequency domain ( 8,9 ) on a portion of the received signal essentially corresponding to the symbol, said transforms being performed with a determined time lag ( 10 ) therebetween: estimating the parameters (r 0 , r 1 , . . . , r n , r′ 0 , r′ 1 , . . . , r′ n ) of the communication channel from pre-determined binary information contained in the digital signal; and estimating the symbol from a combination of the result of each of the transforms performed and the estimated communication channel parameters.

This invention relates to the estimation by a receiver of symbolscarried by a digital signal. It more particularly relates to theestimation of transmitted symbols using OFDM (Orthogonal FrequencyDivision Multiplexing) technology.

OFDM technology is a well-known technique that consists of multiplexingthe data to be sent over a communication channel on frequencysub-carriers. The sub-carriers are separated by a guard band so as toreduce the interference therebetween. They are also orthogonal to oneanother due to the fact that the minimum duration of a piece ofinformation carried by each sub-carrier is the inverse of the value ofthe guard band.

OFDM is in particular used in digital audio broadcasting (DAB) anddigital video broadcasting (DVB) systems, high-speed local wirelessnetworks, and DSL (digital subscriber line) wired digital networks.There are also current plans to use this technology in cellularradiocommunication networks such as UMTS (Universal MobileTelecommunication System).

FIG. 1 illustrates the general principles of a transmission carried outusing OFDM technology. A signal carrying data must be transmitted by atransmitter 1, to be received and interpreted by a receiver 2. The datacarried by the signal include a succession of binary elements.

X_(n) designates a quantity of data in series to be transmitted. In afirst step, a module 3 transforms this series stream into a plurality ofN parallel streams X_(n,0), X_(n,1), . . . X_(n,N−1) As an illustration,each of these parallel streams may consist of a set of binary elementshaving a duration equal to T_(u). An inverse fast Fourier transform(IFFT) 4 is then performed in the transmitter 1 from the N parallelstreams X_(n,0), X_(n,1), . . . X_(n, N−1). At the end of thisoperation, an OFDM symbol s_(m) having a duration equal to T_(u) isobtained. This OFDM symbol appears in the form of a set of coded binaryinformation on frequencies separated by a guard band as indicated above.

The OFDM symbol s_(m) is then sent by the transmitter 1 over acommunication channel 5 which may be of various types, such as a radiochannel for example. The receiver 2 tuned to the channel 5 then receivesa symbol ŝ_(m) corresponding to the transmitted OFDM symbol s_(m),except for disturbances introduced by the channel or by externalinterferences.

A fast Fourier transform 6, or FFT, is then performed on the portion ofthe received signal corresponding to the symbol ŝ_(m). Data elements{circumflex over (X)}_(n,0), {circumflex over (X)}_(n,1), . . .{circumflex over (X)}_(n,N−1) are estimated from said symbol, each dataelement corresponding to the data transmitted by a given frequencysub-carrier. Then a parallel-to-series conversion 7 makes it possible toobtain an estimate {circumflex over (X)}_(n) of the transmitted dataX_(n).

In addition, it is common to use a guard time interval in each OFDMsymbol in order to reduce inter-symbol interference (ISI). In effect,when the communication channel over which the signal is sent containsmultiple paths, as is generally the case for a radio channel, the signalmay be received several times at the receiver with respective delayscorresponding to the various paths. This therefore results in somedegree of overlap between signal portions relating to successive OFDMsymbols, liable to make estimating the transmitted data more difficultand therefore to degrade the quality of the reception.

The guard time interval therefore consists of increasing the duration ofeach pertinent OFDM symbol by duplicating at the end of the symbol somebinary elements placed at the beginning of that symbol, or vice-versa.The duration T_(s) of such an elongated symbol is equal to T_(u)+T_(g),where T_(g) designates the duration of the guard time interval selectedto offset the overlap between the signal portions relating to successiveOFDM symbols. The receiver then takes advantage of the duplication ofsome binary elements in order to improve the estimate of the pertinentdata from each symbol.

When a signal carrying OFDM symbols is received, a problem occurs inminimizing the residual ISI in spite of the use of a guard time intervalin the symbols as indicated above. It involves positioning in time theFFT calculation window for each OFDM symbol received, said window havinga duration equal to T_(u) i.e., less than the duration T_(s)=T_(u)+T_(g)of an OFDM symbol including a guard time interval. In effect, even whenseveral signal echoes corresponding to respective paths of thecommunication channel are received at the receiver, only one FFT isperformed for each OFDM symbol.

The positioning of the time window on which the FFT is performed for agiven symbol is therefore a delicate question, because it depends on thenumber of paths on the channel involved, the quantity of energy receivedrelative to each of the paths, and the time-distribution of said paths.Furthermore, the poor positioning of this window is liable to severelydegrade the reception quality of the transmitted signal because of theISI created by the presence in that window of signal portions relatingto symbols other than the symbol being estimated.

This problem has been studied, for example in the article “OFDMreceivers; impact on coverage of inter-symbol interference and FFTwindow positioning” by R. Brugger and D. Hemingway, published in the“EBU technical review” in July 2003. This article proposes severalstrategies for positioning the FFT calculation window in a digital audio(DAB) or video (DVB) broadcasting system, and assesses the performanceof each such strategy, particularly in terms of inter-symbolinterference.

In this article, a pulse response from the communication channel isestimated in order to identify the principal paths traveled by thetransmitted signal, then the FFT calculation window is respectivelypositioned according to one of the following strategies: relative to thepath exhibiting the highest energy, relative to the first pathexhibiting an energy higher than a threshold, relative to a center ofgravity obtained from the various identified paths, or relative to apath exhibiting a maximum signal-to-interference ratio.

However, inter-symbol interference still exists in the various disclosedstrategies for positioning the FFT calculation window.

In addition, these strategies rely on static criteria, determined onceand for all. They are well-suited for communication channels that varylittle, i.e., in which the path distribution is essentially constant.However, when the communication channel involved is a channel used in amobile radiocommunication system, it can be very changeable over timedepending, for example, on the mobility of the transmitter or thereceiver, and on the environment. In this case, an initial determinationof the time positioning of the FFT calculation window using a staticcriterion could quickly become inappropriate.

One objective of this invention is to mitigate the aforesaiddisadvantages.

Another objective of the invention is to improve the estimate of thesymbols carried by a signal received by a receiver when OFDM technologyis used.

Another objective of the invention is to improve the estimate of thesymbols carried by a signal sent over a communication channel whosecharacteristics vary, such as a radio channel in a mobileradiocommunication system.

The invention thus proposes a method of estimating the symbols carriedby a digital signal received by a receiver over a communication channel,the symbols being multiplexed on orthogonal frequency sub-carriers. Themethod comprises the following steps relating to each symbol carried bythe digital signal:

-   -   perform at least two transforms towards the frequency domain on        a portion of the received signal essentially corresponding to        said symbol, said transforms being performed with a given time        lag therebetween;    -   estimate parameters of the communication channel from        predetermined binary information contained in the digital        signal; and    -   estimate said symbol from a combination of the result of each of        the transforms performed and the estimated communication channel        parameters.

The calculation and the combination of two or more transforms, forexample fast Fourier transforms, staggered in time, makes it possible toobtain pertinent data over a longer time span, which increases thereliability of the estimate of the data contained in the OFDM symbolstransmitted.

The method may, for example, be used in a mobile radiocommunicationsystem. In this case, the communication channel involved is a radiochannel.

The time lag between the transforms can be determined, for example, fromthe characteristics of an environment in which the communication channelis located. It may also be selected based on an analysis of theestimated pulse response of the communication channel.

The time positioning of the calculation window of a first FFT may alsobe selected based on the estimated pulse response of the communicationchannel.

The invention also proposes a receiver containing means to implement theaforesaid method.

The invention further proposes a computer program product to beinstalled in a receiver, including instructions for implementing saidmethod when running the program using means of processing of thereceiver.

Other particularities and benefits of this invention will appear in thefollowing description of non-limiting examples of implementation,referring to the attached drawings, in which:

FIG. 1, already commented, is a diagram illustrating a signaltransmission-reception sequence using OFDM multiplexing technology;

FIG. 2 is a diagram illustrating a receiver according to the invention;

FIG. 3 is a diagram illustrating an example of implementation of theinvention.

Consider a receiver capable of receiving digital signals carryingmultiplexed symbols according to OFDM technology. Said receiver may, forexample, be part of a communication station of a wired communicationsystem. In another embodiment illustrated in FIG. 2, the receiver ispart of a mobile communication system, for example a base station or amobile terminal supporting UMTS technology. In this case, it receivesdigital radio signals at an antenna or an array of antennas 16.

The stream of data received at the receiver in FIG. 2 contains symbolsŝ_(m) corresponding to respective OFDM symbols s_(m) carried by portionsof the signal transmitted over the communication channel to which thereceiver is tuned.

For each OFDM symbol ŝ_(m) received having a duration T_(s)=T_(u)+T_(g),a first fast Fourier transform, called LFFT 8 (for Left FFT), isperformed on a portion of the signal carrying that symbol. Thecalculation window for LFFT 8, i.e., the time span having a durationT_(u) over which the LFFT 8 is performed, can be positioned in variousways. Said positioning may, for example, be the result of one of themethods described in the prior art. An advantageous example ofpositioning such a window will be described in greater detail below.

In addition, a second fast Fourier transform, called RFFT 9 (for RightFFT), is performed on the portion of the signal carrying the same OFDMsymbol. The position of the calculation window of the RFFT 9 isestablished relative to the previously determined position of the LFFT8. In effect, a time lag 10 is selected, to be observed between the LFFT8 and the RFFT 9.

This time lag 10 may be fixed. In this case, it will be advantageouslyselected based on the characteristics of the environment containing thecommunication channel over which the signal is sent. In effect, someenvironments, for example relatively dense urban environments, fostermultiple reflections and diffractions of radio signals, which favors thedispersal of the paths of propagation over time. However, dispersal ofpaths of propagation is a factor of inter-symbol interference (ISI), asexplained above. In order to limit ISI, a relatively long time lag 10 isselected in this type of environment so that the LFFT 8 and the RFFT 9calculation windows are spread over a sufficient period of time to coverthe principal paths of propagation followed by the signal portioninvolved.

Inversely, other environments do not foster the dispersal of paths ofpropagation. These include, for example, rural type environments, wheresignals are most often propagated in a line of sight. This is also thecase in wired systems, where the propagation times generally varylittle. For such environments, a shorter time lag 10 can be selected,for example on the order of the duration of just a few binary elements.

It is also possible to perform other FFTs in addition to the LFFT 8 andthe RFFT 9. In this case, these FFTs are also differently positioned intime, each exhibiting a certain time lag relative to the LFFT 8, forexample.

In one advantageous embodiment of the invention, the LFFT 8 and the RFFT9, as well as any other FFTs, are dynamically positioned in time basedon an analysis of the pulse response 11 of the communication channeltraveled by the signal sent. This embodiment is particularly interestingwhen the communication channel is a radio channel and the communicationsystem to which the receiver belongs is mobile.

The pulse response 11 of the communication channel is calculated by thereceiver. Advantageously, such a calculation is performed several times,for example periodically, in order to have an up-to-date estimate thattakes account of the changes in the profile of propagation. In thiscase, the calculation can be performed for each OFDM symbol transmitted,i.e., with a period approximately equal to T_(s). However, a longerperiod may also be used, when the characteristics of the channel varyless.

The pulse response 11 of the communication channel is calculatedaccording to a conventional method. For example, the receiver involvedis a rake receiver. Such a receiver estimates the pulse response of theradio channel by a series of peaks, each peak appearing with a delaycorresponding to the propagation time along a specific path and having acomplex amplitude corresponding to the attenuation and dephasing of thesignal along that path (instantaneous fading).

A pilot channel can be provided to estimate the pulse response in theform of a succession of peaks. The pulse response is estimated by meansof an adapted filter. For example, when a coded distribution accesstechnique is used, such as the CDMA (Code Division Multiple Access) usedin the UMTS system, the filter is adapted to a pilot spread code withwhich the transmitter modulates a sequence of known symbols, for example1 symbols. The positions of the maximums of the output of this adaptedfilter give the delays used in the fingers of the rake receiver, and theassociated complex amplitudes correspond to the values of said maximums.

The output of the adapted filter is then analyzed. This analysisconsists of statistical calculations on the output of the adapted filter11 to determine the delays (τ_(i))_(0≦i≦M−1) associated with the M pathsor echoes observed, as well as the average receiving energies(E_(i))_(0≦i≦M−1) associated with said paths.

The highest-energy paths detected correspond to principal pathsdependent upon the environment. The highest-energy path will correspond,for example, to a direct path between the transmitter and the receiverif they are in direct visibility to one another. The other principalechoes will schematically be those that yield the fewest reflections anddiffractions between the transmitter and the receiver.

The energy E_(i) associated with a path is the mathematical expectationof the square of the module of the instantaneous amplitude A_(i)(t) ofreception on the corresponding path of propagation.

FIG. 3 schematically illustrates the principal paths, for example thepaths on which an energy higher than a threshold is detected relative tothe radio channel involved. Three paths are seen, characterized by theirrespective delays τ₀, τ₁ and τ₂ with respect to a time reference (whichitself may be determined relative to a first detected path) and by theirrespective energy levels E₀, E₁, and E₂.

In this embodiment, the estimate of the pulse response 11 is used toposition the LFFT 8 and RFFT 9 calculation windows. For example, theLFFT 8 window is positioned relative to the first detected path. Forexample, it begins with a delay approximately equal to τ₀ relative to atime reference, so as to cover the energy peak relating to the firstdetected path. This is what is shown in FIG. 3.

In addition, as was described above, the calculation window of the RFFT9 is positioned relative to that of the LFFT 8 by a time lag 10.Advantageously, this time lag 10 is adjusted based on the estimatedpulse response 11, as illustrated in FIG. 2. For example, this time lag,called D in FIG. 3, is selected so that the RFFT 9 window is positionedrelative to the last detected path in the pulse response 11, for exampleso as to end approximately at the time corresponding to the delay 2relative to said last path.

In the example illustrated in FIG. 3, it can therefore be seen that theLEFT and RFFT calculation windows are positioned so as to spread overtime spans covering the principal paths of propagation characterizingthe radio channel then being considered. This ensures that the two FFTswill be calculated over spans where a large quantity of energy from thesignal portion involved is received. In addition, there is some degreeof overlap between the calculation windows of the two FFTs, which makesit possible to increase the reliability of the calculation, as will bebetter understood by reading the continuation of the description.

Of course, other positionings of the fast Fourier transform calculationwindows can be applied. For example, the RFFT 9 can be calculated on awindow that ends after .tau..sub.2, so as to ensure that the echo of thesignal portion involved corresponding to the last path on the radiochannel will actually be received this window.

Referring to FIG. 2, the use of the FFT calculations performed isdescribed below. As indicated above, each FFT makes it possible toestimate data elements {circumflex over (X)}_(n,0), {circumflex over(X)}_(n,1), . . . {circumflex over (X)}_(n,N−1) each corresponding toone of the frequency sub-carriers used, in order to obtain an estimate{circumflex over (X)}_(n) of the transmitted data X_(n) corresponding tothe content of the OFDM symbol Ŝ_(m) received.

Furthermore, for each FFT calculated, an estimate is made of the radiochannel over which the signal is sent. So an estimate of channel 12 ismade at the output of the calculation module of the LEFT 8 and anestimate of channel 13 is made at the output of the calculation moduleof the RFFT 9. Numerous known methods can be used to estimate thechannel. For example, the least squares method can be used.

According to this last method, the channel estimate module 12 estimatesparameters r₀, r₁, . . . , r_(n) corresponding to disturbances appearingon the radio channel, such that {circumflex over(X)}_(k)=r₀X_(k)+r₁X_(k−1)+ . . . r_(n)X_(k−n)+W_(k), where k is aninteger greater than n, X_(i) is the data corresponding to the i^(th)OFDM symbol transmitted (X_(i) may, for example, be the X_(n) of FIG.1), {circumflex over (X)}_(k) is the estimate corresponding to thek^(th) OFDM symbol received, which follows the calculation of the LFFT 8(for example, {circumflex over (X)}_(n) in FIG. 1), and W_(k) is a firstestimate of the noise affecting the radio channel over which the OFDMsymbols are being sent. In order to estimate the parameters r₀, r₁, . .. , r_(n), pilot bits transmitted over the radio channel and known tothe receiver are conventionally used.

Similarly, the channel estimate module 13 estimates parameters R′₀, r′₁,. . . , r′_(n), such that {circumflex over (X)}_(k)=r′₀X_(k)+r′₁X_(k−1)+. . . r′_(n)X_(k−n)+W′_(k), where k is an integer greater than n,{circumflex over (X)}_(k) is the estimate corresponding to the k^(th)OFDM symbol received, which follows the calculation of the RFFT 9, andw′_(k) is a second estimate of the noise affecting the radio channelover which the OFDM symbols are being sent.

A combination module 14 is then used to make an estimate of the datacorresponding to the OFDM symbols sent, on the basis of the elementssent by the channel estimate modules 12 and 13. If the least squaresmethod has been used to estimate the channel, the module 14 can thenproceed as follows. A vector {circumflex over (X)} is defined as aconcatenation of the 2k+2 estimates {circumflex over (X)}₀, {circumflexover (X)}₁, . . . , {circumflex over (X)}_(k) and {circumflex over(X)}₀, {circumflex over (X)}₁, . . . , {circumflex over (X)}_(k) madeafter the channel estimates made respectively by the modules 12 and 13.In addition, a first convolution matrix R is defined based on theparameters r₀, r₁, . . . , r_(n) estimated by the channel estimatemodule 12. This matrix R, whose dimensions are (k+1)(k+1), has thefollowing structure:

$R = \begin{pmatrix}r_{0} & 0 & 0 & \ldots & \ldots & \ldots & \ldots & \ldots & \ldots & 0 \\r_{1} & r_{0} & 0 & \; & \; & \; & \; & \; & \; & 0 \\r_{2} & r_{1} & r_{0} & \ldots & \; & \; & \; & \; & \; & 0 \\\ldots & r_{2} & r_{1} & \ldots & \ldots & \; & \; & \; & \; & 0 \\r_{n} & \ldots & r_{2} & \ldots & \ldots & \ldots & \; & \; & \; & 0 \\0 & r_{n} & \ldots & \ldots & \ldots & \ldots & \ldots & \; & \; & 0 \\0 & 0 & r_{n} & \; & \ldots & \ldots & \ldots & \ldots & \; & 0 \\0 & 0 & 0 & \ldots & \; & \ldots & \ldots & \ldots & \ldots & \ldots \\\ldots & \ldots & \ldots & \ldots & \ldots & \; & \ldots & \ldots & \ldots & 0 \\0 & 0 & 0 & \ldots & 0 & r_{n} & \ldots & r_{2} & r_{1} & r_{0}\end{pmatrix}$

Similarly, a second convolution matrix R′ is defined based on theparameters r′₀, r′₁, . . . , r′_(n) estimated by the channel 13 estimatemodule. This matrix R′, whose dimensions are (k+1)*(k+1), has thefollowing structure:

$R = {\begin{pmatrix}r_{0}^{\prime} & 0 & 0 & \ldots & \ldots & \ldots & \ldots & \ldots & \ldots & 0 \\r_{1}^{\prime} & r_{0}^{\prime} & 0 & \; & \; & \; & \; & \; & \; & 0 \\r_{2}^{\prime} & r_{1}^{\prime} & r_{0}^{\prime} & \ldots & \; & \; & \; & \; & \; & 0 \\\ldots & r_{2}^{\prime} & r_{1}^{\prime} & \ldots & \ldots & \; & \; & \; & \; & 0 \\r_{n}^{\prime} & \ldots & r_{2}^{\prime} & \ldots & \ldots & \ldots & \; & \; & \; & 0 \\0 & r_{n}^{\prime} & \ldots & \ldots & \ldots & \ldots & \ldots & \; & \; & 0 \\0 & 0 & r_{n}^{\prime} & \; & \ldots & \ldots & \ldots & \ldots & \; & 0 \\0 & 0 & 0 & \ldots & \; & \ldots & \ldots & \ldots & \ldots & \ldots \\\ldots & \ldots & \ldots & \ldots & \ldots & \; & \ldots & \ldots & \ldots & 0 \\0 & 0 & 0 & \ldots & 0 & r_{n}^{\prime} & \ldots & r_{2}^{\prime} & r_{1}^{\prime} & r_{0}^{\prime}\end{pmatrix}.}$

Lastly, a vector X is defined, which includes all the k+1 quantities ofdata X₀, X₁, . . . , X_(k) corresponding to the OFDM symbols sent, whichneed to be determined.

It is then possible to write the following equation: {circumflex over(X)}=M·X, where M represents a column concatenation matrix of the blockmatrices R and R′, i.e.,

$M = {\begin{pmatrix}R \\R^{\prime}\end{pmatrix}.}$

This matrix M thus has 2k+2 lines and k+1 columns.

The noises w_(k) and w′_(k) introduced above are delayed from oneanother due to the lag 10 existing between the two FFTs performed, sothey are independent and do not enter into the equation system to detectthe value of the symbols sent.

The vector X can then be estimated as the product of (M^(H)M)⁻¹.M^(H).{circumflex over (X)}, where the operator (.)^(H) is theconjugated transpose.

Of course, many methods other than the least squares method can be usedto estimate the channel. In this case, the estimate of the vector X willbe adapted to the method used (for example, one of the followingmethods: a posteriori maximum, MLSE (Maximum Likelihood SequenceEstimator), Viterbi algorithm, etc.).

Once the combination is performed by the module 14, an estimate isobtained of the data X₀, X₁, . . . , X_(k) corresponding to the signalssent. The reliability of this estimate is greater than that of thoseobtained by conventional methods because it relies on a combination ofestimates made as a result of two different observations. Furthermore,as was indicated above, the time lag between the FFTs makes it possibleto achieve some data redundancy which is taken advantage of in thecombination 14, all the while ensuring that the final estimate is basedon the highest-energy, and therefore the most significant, echoes.

It will be noted that the principles discussed above can be implementedby using a computer program containing the corresponding instructionsand run, for example, by a processing unit in the receiver involved.

1-22. (canceled)
 23. A mobile terminal for receiving a digital signaltransmitted over a communication channel, the symbols being multiplexedon orthogonal frequency sub-carriers, the mobile terminal, comprising:channel estimation logic operable to estimate at least one communicationchannel parameter from predetermined information contained in thedigital signal; transform logic operable for each symbol: to perform atransform on a first portion of the received signal to provide a firstset of frequency domain parameters, the first portion substantiallycorresponding to at least part of the symbol; to perform a transform ona second portion of the received signal to provide a second set offrequency domain parameters, the second portion substantiallycorresponding to at least part of the symbol; and the first and secondportions being separated a predetermined time shift; and symbolestimation logic operable for each symbol to estimate the symbol from acombination of the first and second sets of frequency domain parametersand the at least one estimated communication channel parameter.
 24. Themobile terminal of claim 23, wherein the channel estimation logic isoperable to estimate an impulse response of the communication channel.25. The mobile terminal of claim 23, wherein the channel estimationlogic is operable to estimate an impulse response of the communicationchannel, and wherein the time shift between the first and secondportions of the received signal on which the transform is performed isbased on the estimated impulse response of the communication channel.26. The mobile terminal of claim 25, further comprising: delaydetermination logic operable to determine a delay between energy peaksin the estimated impulse response; and time shift setting logic operableto set the predetermined time shift based on the determined delay. 27.The mobile terminal of claim 24, wherein the transform logic is operableto perform the transform on at least one portion of the signal that issubstantially shorter than a duration of a symbol.
 28. The mobileterminal of claim 24, wherein the channel estimation logic is operableto estimate the impulse response of the communication channelperiodically.
 28. The mobile terminal of claim 23, wherein: the channelestimation logic is operable to estimate at least one communicationchannel parameter from predetermined information contained in thedigital signal by: estimating the communication channel based on thetransform performed on the first portion to obtain a first set ofestimated communication channel parameters; and estimating thecommunication channel based on the transform performed on the secondportion to obtain a second set of estimated communication channelparameters; and the symbol estimation logic is operable to estimate thesymbol from a combination of the first and second sets of frequencydomain parameters and the at least one estimated communication channelparameter by estimating the symbol from a combination of the first andsecond sets of frequency domain parameters and the first and second setsof estimated communication channel parameters.
 29. The mobile terminalof claim 28, wherein the channel estimation logic is operable toestimate the communication channel by using a channel estimationtechnique selected from a group consisting of: least squares method;maximum a posteriori method; maximum likelihood sequence estimatormethod; and Viterbi method.
 30. The mobile terminal of claim 23, whereinthe transform logic is operable to perform Fast Fourier transforms. 31.The mobile terminal of claim 23, wherein the time shift is performed ispredetermined based on characteristics of an environment in which thecommunication channel is located.
 32. The mobile terminal of claim 23,wherein the communication channel is a radio channel.
 33. The mobileterminal of claim 23, further comprising a receiver, the receivercomprising the channel estimation logic, the transform logic and thesymbol estimation logic.
 34. A mobile terminal for receiving a digitalsignal transmitted over a communication channel, the symbols beingmultiplexed on orthogonal frequency sub-carriers, the mobile terminalcomprising: channel estimation logic operable to estimate at least onecommunication channel parameter from predetermined information containedin the digital signal; transform logic operable for each symbol: toperform a transform at least one portion of the received signal that issubstantially shorter than a duration of a symbol; to perform atransform on a first portion of the received signal to provide a firstset of frequency domain parameters, the first portion substantiallycorresponding to at least part of the symbol; to perform a transform ona second portion of the received signal to provide a second set offrequency domain parameters, the second portion substantiallycorresponding to at least part of the symbol; and the first and secondportions being separated a predetermined time shift; and symbolestimation logic operable for each symbol to estimate the symbol from acombination of the first and second sets of frequency domain parameters,and the at least one estimated communication channel parameter.
 35. Themobile terminal of claim 34, wherein the channel estimation logic isoperable to estimate an impulse response of the communication channel.36. The mobile terminal of claim 34, wherein the channel estimationlogic is operable to estimate an impulse response of the communicationchannel, and wherein the time shift between the first and secondportions of the received signal on which the transform is performed isbased on the estimated impulse response of the communication channel.37. The mobile terminal of claim 36, further comprising: delaydetermination logic operable to determine a delay between energy peaksin the estimated impulse response; and time shift setting logic operableto set the predetermined time shift based on the determined delay. 38.The receiver of claim 34, wherein the channel estimation logic isoperable to estimate the impulse response of the communication channelperiodically.
 39. A method comprising, receiving, by a mobile terminal,symbols carried by a digital signal, the symbols being multiplexed onorthogonal frequency sub-carriers; estimating at least one communicationchannel parameter from predetermined information contained in thedigital signal; transforming on a first portion of the received signalto provide a first set of frequency domain parameters, the first portionsubstantially corresponding to at least part of the symbol; transformingon a second portion of the received signal to provide a second set offrequency domain parameters, the second portion substantiallycorresponding to at least part of the symbol; and the first and secondportions being separated a predetermined time shift; and estimating, forat least one symbol, the symbol from a combination of the first andsecond sets of frequency domain parameters and the at least oneestimated communication channel parameter.
 40. The method of claim 39,wherein the communication channel is a radio channel.
 41. The method ofclaim 39, wherein estimating at least communication channel comprisesestimating an impulse response of the communication channel.
 42. Themethod of claim 39, wherein estimating at least communication channelcomprises estimating an impulse response of the communication channel,and wherein the time shift is based on the estimated impulse response ofthe communication channel.